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aat2506 1mhz step-down converter/ldo regulator 2506.2005.12.1.0 1 syspwr ? typical application aat2506 step-down converter efficiency (v out = 2.5v; l = 10 h) output current (ma) efficiency (%) 60 70 80 90 100 0.1 1 10 100 1000 v in = 3.3v 4.7 h l1 c1 22 f 2.2 f c4 10 f c3 10nf c5 pgnd 1 lx 2 vp 3 vcc 4 enldo 9 en 10 fb 11 sgnd 12 vldo 5 out 6 gnd 8 byp 7 aat2506 u1 l1 sumida cdrh3d16-4r7 c1 murata grm219r61a475ke19 c3 murata grm21br60j106ke19 v in = 2.7v to 5.5v 3.3v at 300ma general description the aat2506 is a member of analogictech's total power management ic? (tpmic?) product fam- ily. it is a low dropout (ldo) linear regulator and a step-down converter with an input voltage range of 2.7v to 5.5v, making it ideal for applications with single lithium-ion/polymer batteries. the ldo has an independent input and is capable of delivering up to 300ma. the linear regulator has been designed for high-speed turn-on and turn-off performance, fast transient response, and good power supply rejection ratio (psrr). other fea- tures include low quiescent current and a low dropout voltage. the aat2506 is available in either a fixed version with internal feedback or a programmable version with external feedback resistors. it can deliver 600ma of load current while maintaining a low 25a no load quiescent current. the 1mhz switch- ing frequency minimizes the size of external com- ponents while keeping switching losses low. the aat2506 feedback and control delivers excellent load regulation and transient response with a small output inductor and capacitor. the aat2506 is designed to maintain high efficien- cy throughout the operating range, which is critical for portable applications. the aat2506 is available in a 12-pin tdfn33 package, and is rated over a temperature range of -40c to +85c. features ?v in range: 2.7v to 5.5v ?v out range: 0.6v to v in ? 300ma ldo current output ? 400mv ldo dropout voltage at 300ma ? high output accuracy: 1.5% ? fast ldo line / load transient response ? 600ma, 97% efficiency step-down converter ? fast turn-on time (100s typical) ? 25a no load quiescent current for step- down converter ? shutdown current <1a ? low r ds(on) 0.4 ? integrated power switches ? 100% duty cycle low dropout operation ? 1mhz switching frequency ? 100s typical soft start ? over-temperature protection ? current limit protection ? available in tdfn33-12 package ? -40c to +85c temperature range applications ? cellular phones ? digital cameras ? handheld instruments ? microprocessor/dsp core/io power ? pdas and handheld computers ? portable media players
aat2506 1mhz step-down converter/ldo regulator 2 2506.2005.12.1.0 pin descriptions pin configuration tdfn33-12 (topview) pgnd lx vp 1 vcc vldo out sgnd fb en enldo gnd byp 2 3 4 5 6 12 11 10 9 8 7 pin # symbol function 1 pgnd step-down converter power ground return pin. connect to the output and input capaci- tor return. see section on pcb layout guidelines and evaluation board layout diagram. 2 lx power switching node. output switching node that connects to the output inductor. 3 vp step-down converter power stage supply voltage. must be closely decoupled to pgnd. 4 vcc step-down converter bias supply. connect to vp. 5 vldo ldo input voltage; should be decoupled with 1f or greater capacitor. 6 out 300ma ldo output pin. a 2.2f or greater output low-esr ceramic capacitor is required for stability. 7 byp bypass capacitor for the ldo. to improve ac ripple rejection, connect a 10nf capaci- tor to gnd. this will also provide a soft-start function. 8 gnd ldo ground connection pin. 9 enldo enable pin for ldo. when connected low, ldo is disabled and consumes less than 1a of current. 10 en step-down converter enable. when connected low, ldo is disabled and consumes less than 1a. 11 fb step-down converter feedback input pin. for fixed output voltage versions, this pin is connected to the converter output, forcing the converter to regulate to the specific volt- age. for adjustable output versions, an external resistive divider ties to this point and programs the output voltage to the desired value. 12 sgnd step-down converter signal ground. for external feedback, return the feedback resis- tive divider to this ground. for internal fixed version, tie to the point of load return. see section on pcb layout guidelines and evaluation board layout diagram. ep exposed paddle (bottom). use properly sized vias for thermal coupling to the ground plane. see section on pcb layout guidelines.
aat2506 1mhz step-down converter/ldo regulator 2506.2005.12.1.0 3 absolute maximum ratings 1 thermal information symbol description value units p d maximum power dissipation 2 w ja thermal resistance 2 50 c/w symbol description value units v p , v ldo input voltages to gnd 6.0 v v lx lx to gnd -0.3 to v p + 0.3 v v fb fb to gnd -0.3 to v p + 0.3 v v en en to gnd -0.3 to 6.0 v t j operating junction temperature range -40 to 150 c t lead maximum soldering temperature (at leads, 10 sec) 300 c 1. stresses above those listed in absolute maximum ratings may cause permanent damage to the device. functional operation at conditions other than the operating conditions specified is not implied. only one absolute maximum rating should be applied at any one time. 2. mounted on an fr4 board with exposed paddle connected to ground plane.
aat2506 1mhz step-down converter/ldo regulator 4 2506.2005.12.1.0 electrical characteristics 1 symbol description conditions min typ max units ldo v in = v ldo = v out(nom) + 1v for v out options greater than 1.5v. v in = v ldo = 2.5v for v out 1.5v. i out = 1ma, c out = 2.2f, c in = 1f, t a = -40c to +85c, unless otherwise noted. typical values are t a = 25c. t a = 25c -1.5 1.5 v out output voltage tolerance i out = 1ma to 300ma t a = -40c -2.5 2.5 % to 85c v in input voltage v out +v do 2 5.5 v v do dropout voltage 3, 4 i out = 300ma 400 600 mv ? v out / line regulation v in = v out + 1v to 5v 0.09 %/v v out * ? v in ? v out(line) dynamic line regulation i out = 300ma, v in = v out + 1v to 2.5 mv v out + 2v, t r /t f = 2s ? v out(load) dynamic load regulation i out = 1ma to 300ma, t r <5s 60 mv i out output current v out > 1.3v 300 ma i sc short-circuit current v out < 0.4v 600 ma i qldo ldo quiescent current v in = 5v, no load, enldo = v in 70 125 a i shdn shutdown current v in = 5v; enldo = gnd, 1.0 a en = sgnd = pgnd 1khz 67 psrr power supply rejection ratio i out = 10ma, c byp = 10nf 10khz 47 db 1mhz 45 t sd over-temperature shutdown 145 c threshold t hys over-temperature shutdown 12 c hysteresis e n output noise e nbw = 300hz to 50khz 50 v rms t c output voltage temperature 22 ppm/c coefficient 1. the aat2506 is guaranteed to meet performance specifications over the -40c to +85c operating temperature range and is assu red by design, characterization, and correlation with statistical process controls. 2. to calculate the minimum ldo input voltage, use the following equation: v in(min) = v out(max) + v do(max) , as long as v in 2.5v. 3. for v out <2.1v, v do = 2.5 - v out . 4. v do is defined as v in - v out when v out is 98% of nominal.
aat2506 1mhz step-down converter/ldo regulator 2506.2005.12.1.0 5 electrical characteristics 1 symbol description conditions min typ max units buck converter typical values are t a = 25c, v in = v cc = v p = 3.6v. v in input voltage 2.7 5.5 v v in rising 2.6 v v uvlo uvlo threshold hysteresis 100 mv v in falling 1.8 v v out output voltage tolerance i out = 0 to 400ma, -3.5 +3.5 % v in = 2.7v to 5.5v v out output voltage range fixed output version 0.6 4.0 v i qbuck step-down converter enldo = gnd, no load, 25 50 a quiescent current 0.6v adjustable model i shdn shutdown current en = sgnd = pgnd, enldo = gnd 1.0 a i lim p-channel current limit 600 ma r ds(on)h high side switch on 0.45 ? resistance r ds(on)l low side switch on 0.40 ? resistance i lxlk lx leakage current v in = 5.5v, v lx = 0 - v in 1.0 a en = sgnd = pgnd i lxlk, r lx reverse leakage current v in = open, v lx = 5.5v, 1.0 a (fixed) en = sgnd = pgnd v linereg line regulation v in = 2.7v to 5.5v 0.5 %/v v fb fb threshold voltage 0.6v output, no load, t a = 25c 591 600 609 mv accuracy i fb fb leakage current 0.6v output 0.2 a f osc oscillator frequency t a = 25c 0.7 1.0 1.5 mhz t s start-up time from enable to output regulation 100 s t sd over-temperature shutdown 140 c threshold t hys over-temperature shutdown 15 c hysteresis logic signals v en(l) enable threshold low 0.6 v v en(h) enable threshold high 1.5 v i en(h) leakage current 1.0 1.0 a 1. the aat2506 is guaranteed to meet performance specifications over the -40c to +85c operating temperature range and is assu red by design, characterization, and correlation with statistical process controls.
typical characteristics unless otherwise noted, v in = 5v, t a = 25c. ldo initial power-up response time (c byp = 10nf; en = gnd; enldo = v in ) 400 s/div v enldo (5v/div) v out (1v/div) ldo dropout voltage vs. temperature (en = gnd; enldo = v in ) 0 60 120 180 240 300 360 420 480 540 -40 -30 -20 -10 0 10 20 30 40 50 60 70 80 90 100 110 120 temperature ( c) dropout voltage (mv) i l = 300ma i l = 150ma i l = 100ma i l = 50ma ldo ground current vs. input voltage (en = gnd; enldo = v in ) 0.00 10.00 20.00 30.00 40.00 50.00 60.00 70.00 80.00 90.00 2 2.5 3 3.5 4.5 45 input voltage (v) ground current ( a) i out =0ma i out =10ma i out =50ma i out =150ma i out =300ma ldo dropout voltage vs. output current (en = gnd; enldo = v in ) 0 50 100 150 200 250 300 350 400 450 500 0 50 100 150 200 250 300 output current (ma) dropout voltage (mv) 85 c 25 c -40 c ldo dropout characteristics (en = gnd; enldo = v in ) 2.00 2.20 2.40 2.60 2.80 3.00 3.20 2.70 2.80 2.90 3.00 3.10 3.20 3.30 input voltage (v) output voltage (v) i out = 300ma i out = 150ma i out = 100ma i out = 50ma i out = 10ma i out = 0ma ldo dropout voltage vs. temperature (en = gnd; enldo = v in ) 0 60 120 180 240 300 360 420 480 540 -40 -30 -20 -10 0 10 20 30 40 50 60 70 80 90 100 110 120 temperature ( c) dropout voltage (mv) i l = 300ma i l = 150ma i l = 100ma i l = 50ma aat2506 1mhz step-down converter/ldo regulator 6 2506.2005.12.1.0
typical characteristics unless otherwise noted, v in = 5v, t a = 25c, v in = v ldo = v cc = v p . ldo self noise (en = gnd; enldo = v in ) 0.001 0.01 0.1 1 10 0.01 0.1 1 10 100 1000 10000 frequency (khz) noise amplitude ( v/rthz) band power: 300hz to 50khz = 44.6 vrms 100hz to 100khz = 56.3 vrms ldo load transient response 300ma (c byp = 10nf; en = gnd; enldo = v in ) 2.10 2.20 2.30 2.40 2.50 2.60 2.70 2.80 2.90 3.00 10 s/div output voltage (v) -100 0 100 200 300 400 500 600 700 800 output current (ma) v out i out ldo load transient response (c byp = 10nf; en = gnd; enldo = v in ) 2.60 2.65 2.70 2.75 2.80 2.85 2.90 100 s/div output voltage (v) -100 0 100 200 300 400 500 output current (ma) v out i out ldo line transient response (c byp = 10nf; en = gnd; enldo = v in ) 2.98 2.99 3.00 3.01 3.02 3.03 3.04 100 s/div input voltage (v) 0 1 2 3 4 5 6 output voltage (v) v in v out ldo turn-on time from enable (v in present) (c byp = 10nf; en = gnd; enldo = v in ) 5 s/div v in = 4v v out = 1v/div v enldo = 5v/div ldo turn-off response time (c byp = 10nf; en = gnd; enldo = v in ) 50 s/div v enldo (5v/div) v out (1v/div) aat2506 1mhz step-down converter/ldo regulator 2506.2005.12.1.0 7
typical characteristics unless otherwise noted, v in = 5v, t a = 25c. step-down converter dc regulation (v out = 2.5v; l = 10 h; enldo = gnd) output current (ma) output error (%) -3.0 -2.0 -1.0 0.0 1.0 2.0 3.0 0.1 1 10 100 1000 v in = 3.6v v in = 3.3v v in = 3.0v step-down converter efficiency vs. load (v out = 2.5v; l = 10 h; enldo = gnd) output current (ma) efficiency (%) 60 70 80 90 100 0.1 1 10 100 1000 v in = 3.0v v in = 3.6v v in = 3.3v step-down converter dc regulation (v out = 3.3v; l = 10 h; enldo = gnd) output current (ma) output error (%) -3.0 -2.0 -1.0 0.0 1.0 2.0 3.0 0.1 1 10 100 1000 v in = 4.2v v in = 3.9v step-down converter efficiency vs. load (v out = 3.3v; l = 10 h; enldo = gnd) output current (ma) efficiency (%) 60 70 80 90 100 0.1 1 10 100 1000 v in = 3.9v v in = 4.2v ldo enldo vs. v in 1.050 1.075 1.100 1.125 1.150 1.175 1.200 1.225 1.250 2.5 3.0 3.5 4.0 4.5 5.0 5.5 input voltage (v) v ih v il over-current protection (en = gnd; enldo = v in ) time (50ms/div) output current (ma) -200 0 200 400 600 800 1000 1200 aat2506 1mhz step-down converter/ldo regulator 8 2506.2005.12.1.0
typical characteristics unless otherwise noted, v in = 5v, t a = 25c. step-down converter input current vs. input voltage (v o = 1.8v; en = v in ; enldo = gnd) input voltage (v) input current ( a) 85 c 25 c -40 c 15 20 25 30 35 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0 step-down converter switching frequency vs. temperature (v in = 3.6v; v o = 1.5v; en = v in ; enldo = gnd) temperature ( c) frequency variation (%) -0.20 -0.10 0.00 0.10 0.20 -40 -20 0 20 40 60 80 100 step-down converter output voltage error vs. temperature (v in = 3.6v; v o = 1.5v; en = v in ; enldo = gnd) temperature ( c) output error (%) -2.0 -1.0 0.0 1.0 2.0 -40 -20 0 20 40 60 80 100 step-down converter frequency vs. input voltage (v out = 1.8v; en = v in ; enldo = gnd) input voltage (v) frequency variation (%) -2.0 -1.5 -1.0 -0.5 0.0 0.5 1.0 2.7 3.1 3.5 3.9 4.3 4.7 5.1 5.5 step-down converter dc regulation (v out = 1.5v; l = 4.7 h; enldo = gnd) output current (ma) output error (%) -3.0 -2.0 -1.0 0.0 1.0 2.0 3.0 0.1 1 10 100 1000 v in = 3.6v v in = 4.2v v in = 2.7v step-down converter efficiency vs. load (v out = 1.5v; l = 4.7 h; enldo = gnd) output current (ma) efficiency (%) 50 60 70 80 90 100 0.1 1 10 100 1000 v in = 3.6v v in = 4.2v v in = 2.7v aat2506 1mhz step-down converter/ldo regulator 2506.2005.12.1.0 9
typical characteristics unless otherwise noted, v in = 5v, t a = 25c. step-down converter line regulation (v out = 1.5v; enldo = gnd) input voltage (v) accuracy (%) -1 -0.5 0 0.5 1 1.5 2 2.5 3 3.5 4 4.5 5 5.5 6 i out = 600ma i out = 100ma i out = 10ma step-down converter line transient (v out = 1.8v @ 400ma; en = v in ; enldo = gnd) output voltage (top) (v) input voltage (bottom) (v) time (25 s/div) 1.50 1.55 1.60 1.65 1.70 1.75 1.80 1.85 1.90 3.0 3.5 4.0 4.5 5.0 5.5 6.0 6.5 7.0 step-down converter load transient response (30ma - 300ma; v in = 3.6v; v out = 2.5v; c1 = 22 f; enldo = gnd) output voltage (top) (v) load and inductor current (200ma/div) (bottom) time (25 s/div) 2.05 2.15 2.25 2.35 2.45 2.55 2.65 -0.1 0.1 0.3 0.5 0.7 0.9 1.1 1.3 1.5 30ma 300ma step-down converter load transient response (30ma - 300ma; v in = 3.6v; v out = 1.5v; c1 = 22 f; enldo = gnd) output voltage (top) (v) load and inductor current (200ma/div) (bottom) time (25 s/div) 1.00 1.05 1.10 1.15 1.20 1.25 1.30 1.35 1.40 1.45 1.50 1.55 1.60 1.65 -0.1 0.1 0.3 0.5 0.7 0.9 1.1 1.3 1.5 30ma 300ma step-down converter n-channel r ds(on) vs. input voltage (en = v in ; enldo = gnd) input voltage (v) r ds(on) (m ? ? ) 300 350 400 450 500 550 600 650 700 750 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0 25 c 120 c 100 c 85 c step-down converter p-channel r ds(on) vs. input voltage (en = v in ; enldo = gnd) input voltage (v) r ds(on) (m ? ? ) 300 350 400 450 500 550 600 650 700 750 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0 25 c 120 c 100 c 85 c aat2506 1mhz step-down converter/ldo regulator 10 2506.2005.12.1.0
typical characteristics unless otherwise noted, v in = 5v, t a = 25c. step-down converter output ripple (v in = 3.6v; v out = 1.8v; 400ma; en = v in ; enldo = gnd) output voltage (ac coupled) (top) (mv) inductor current (bottom) (a) time (250ns/div) -120 -100 -80 -60 -40 -20 0 20 40 0.1 0.2 0.3 0.4 0.5 0.6 0.7 0.8 0.9 step-down converter soft start (v in = 3.6v; v out = 1.5v; l = 4.7 h; enldo = gnd) enable and output voltage (top) (v) inductor current (bottom) (a) time (50 s/div) -4.0 -3.0 -2.0 -1.0 0.0 1.0 2.0 3.0 4.0 -0.5 0.0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 aat2506 1mhz step-down converter/ldo regulator 2506.2005.12.1.0 11
aat2506 1mhz step-down converter/ldo regulator 12 2506.2005.12.1.0 functional block diagram note: internal resistor divider included for 1.2v versions. for low voltage versions, the feedback pin is tied directly to the error amplifier input. en lx error amp. logic dh dl pgnd vp fb gnd voltage reference voltage reference error amp. out control logic vldo fast start control enldo byp sgnd vcc see note over-current protection
aat2506 1mhz step-down converter/ldo regulator 2506.2005.12.1.0 13 functional description the aat2506 is a high performance power man- agement ic comprised of a buck converter and a linear regulator. the buck converter is a high effi- ciency converter capable of delivering up to 600ma. designed to operate at 1.0mhz, the con- verter requires only three external components (c in , c out , and l x ) and is stable with a ceramic output capacitor. the linear regulator delivers 300ma and is also stable with ceramic capacitors. linear regulator the advanced circuit design of the linear regulator has been specifically optimized for very fast start- up and shutdown timing. this proprietary cmos ldo has also been tailored for superior transient response characteristics. these traits are particu- larly important for applications that require fast power supply timing. the high-speed turn-on capability is enabled through implementation of a fast-start control cir- cuit, which accelerates the power-up behavior of fundamental control and feedback circuits within the ldo regulator. fast turn-off time response is achieved by an active output pull-down circuit, which is enabled when the ldo regulator is placed in shutdown mode. this active fast shut- down circuit has no adverse effect on normal device operation. the ldo regulator output has been specifically optimized to function with low- cost, low-esr ceramic capacitors; however, the design will allow for operation over a wide range of capacitor types. a bypass pin has been provided to allow the addi- tion of an optional voltage reference bypass capac- itor to reduce output self noise and increase power supply ripple rejection. device self noise and psrr will be improved by the addition of a small ceramic capacitor in this pin. however, increased values of c bypass may slow down the ldo regula- tor turn-on time. the regulator comes with com- plete short-circuit and thermal protection. the com- bination of these two internal protection circuits gives a comprehensive safety system to guard against extreme adverse operating conditions. the regulator features an enable/disable function. this pin (enldo) is active high and is compatible with cmos logic. to assure the ldo regulator will switch on, the enldo turn-on control level must be greater than 1.5v. the ldo regulator will go into the disable shutdown mode when the voltage on the en pin falls below 0.6v. if the enable function is not needed in a specific application, it may be tied to v in to keep the ldo regulator in a continuously on state. when the regulator is in shutdown mode, an inter- nal 1.5k ? resistor is connected between out and gnd. this is intended to discharge c out when the ldo regulator is disabled. the internal 1.5k ? resistor has no adverse impact on device turn-on time. step-down converter the aat2506 buck is a constant frequency peak current mode pwm converter with internal com- pensation. it is designed to operate with an input voltage range of 2.7v to 5.5v. the output voltage ranges from 0.6v to the input voltage. the 0.6v fixed model shown in figure 1 is also the adjustable version and is externally programmable with a resistive divider, as shown in figure 2. the converter mosfet power stage is sized for 600ma load capability with up to 97% efficiency. light load efficiency exceeds 80% at a 500a load. soft start the aat2506 soft-start control prevents output voltage overshoot and limits inrush current when either the input power or the enable input is applied. when pulled low, the enable input forces the converter into a low-power, non-switching state with a bias current of less than 1a.
aat2506 1mhz step-down converter/ldo regulator 14 2506.2005.12.1.0 low dropout operation for conditions where the input voltage drops to the output voltage level, the converter duty cycle increases to 100%. as 100% duty cycle is approached, the minimum off-time initially forces the high side on-time to exceed the 1mhz clock cycle and reduce the effective switching frequency. once the input drops below the level where the out- put can be regulated, the high side p-channel mosfet is turned on continuously for 100% duty cycle. at 100% duty cycle, the output voltage tracks the input voltage minus the ir drop of the high side p-channel mosfet r ds(on) . low supply the under-voltage lockout (uvlo) guarantees suf- ficient v in bias and proper operation of all internal circuitry prior to activation. fault protection for overload conditions, the peak inductor current is limited. thermal protection disables switching when the internal dissipation or ambient temperature becomes excessive. the junction over-temperature threshold is 140c with 15c of hysteresis. applications information linear regulator input and output capacitors: an input capacitor is not required for basic operation of the linear reg- ulator. however, if the aat2506 is physically locat- ed more than three centimeters from an input power source, a c in capacitor will be needed for stable operation. typically, a 1f or larger capaci- tor is recommended for c in in most applications. c in should be located as closely to the device v in pin as practically possible. an input capacitor greater than 1f will offer supe- rior input line transient response and maximize power supply ripple rejection. ceramic, tantalum, or aluminum electrolytic capacitors may be select- ed for c in . there is no specific capacitor esr requirement for c in . however, for 300ma ldo reg- ulator output operation, ceramic capacitors are rec- ommended for c in due to their inherent capability over tantalum capacitors to withstand input current surges from low impedance sources such as bat- teries in portable devices. for proper load voltage regulation and operational stability, a capacitor is required between out and gnd. the c out capacitor connection to the ldo regulator ground pin should be made as directly as practically possible for maximum device perform- ance. since the regulator has been designed to function with very low esr capacitors, ceramic capacitors in the 1.0f to 10f range are recom- mended for best performance. applications utilizing figure 1: aat2506 fixed output. figure 2: aat2506 with adjustable step-down output and enhanced transient response. l1 22 f c1 v in r1 59k r2 4.7 f c4 10 f c3 10nf c5 v outldo v outbuck 100pf c8 pgnd 1 lx 2 vp 3 vcc 4 enldo 9 en 10 fb 11 sgnd 12 vldo 5 out 6 gnd 8 byp 7 aat2506 u1 l1 22 f c1 v outbuck v in 4.7 f c4 10 f c3 10nf c5 v outldo pgnd 1 lx 2 vp 3 vcc 4 enldo 9 en 10 fb 11 sgnd 12 vldo 5 out 6 gnd 8 byp 7 aat2506 u1
the exceptionally low output noise and optimum power supply ripple rejection should use 2.2f or greater for c out . in low output current applications, where output load is less than 10ma, the minimum value for c out can be as low as 0.47f. equivalent series resistance: esr is a very important characteristic to consider when selecting a capacitor. esr is the internal series resistance asso- ciated with a capacitor that includes lead resistance, internal connections, size and area, material compo- sition, and ambient temperature. typically, capacitor esr is measured in milliohms for ceramic capaci- tors and can range to more than several ohms for tantalum or aluminum electrolytic capacitors. bypass capacitor and low noise applications a bypass capacitor pin is provided to enhance the low noise characteristics of the ldo. the bypass capacitor is not necessary for operation; however, for best device performance, a small ceramic capacitor in the range of 470pf to 10nf should be placed between the bypass pin (byp) and the device ground pin (gnd). to practically realize the highest power supply ripple rejection and lowest output noise performance, it is critical that the capacitor connection between the byp pin and gnd pin be direct and pcb traces should be as short as possible. dc leakage on this pin can affect the ldo regula- tor output noise and voltage regulation perform- ance. for this reason, the use of a low leakage, high quality ceramic (npo or c0g type) or film capacitor is highly recommended. step-down converter inductor selection: the step-down converter uses peak current mode control with slope com- pensation to maintain stability for duty cycles greater than 50%. the output inductor value must be selected so the inductor current down slope meets the internal slope compensation require- ments. the internal slope compensation for the adjustable and low-voltage fixed versions of the aat2506 is 0.24a/sec. this equates to a slope compensation that is 75% of the inductor current down slope for a 1.5v output and 4.7h inductor. this is the internal slope compensation for the adjustable (0.6v) version or low-voltage fixed ver- sions. when externally programming the 0.6v ver- sion to 2.5v, the calculated inductance is 7.5h. in this case, a standard 10h value is selected. for high-voltage fixed versions (2.5v and above), m = 0.48a/sec. table 1 displays inductor values for the aat2506 fixed and adjustable options. 0.75 ? v o l = = 3 ? v o = 3 ? 2.5v = 7.5 h m 0.75 ? v o 0.24a sec a sec a a sec 0.75 ? v o m = = = 0.24 l 0.75 ? 1.5v 4.7 h a sec aat2506 1mhz step-down converter/ldo regulator 2506.2005.12.1.0 15 table 1: inductor values. configuration output voltage inductor slope compensation 0.6v adjustable with 0.6v to 2.0v 4.7h 0.24a/sec external resistive divider 2.5v to v in 10h 0.24a/sec fixed output 0.6v to 2.0v 4.7h 0.24a/sec 2.5v to v in 4.7h 0.48a/sec
aat2506 1mhz step-down converter/ldo regulator 16 2506.2005.12.1.0 manufacturer's specifications list both the inductor dc current rating, which is a thermal limitation, and the peak current rating, which is determined by the saturation characteristics. the inductor should not show any appreciable saturation under normal load conditions. some inductors may meet the peak and average current ratings yet result in excessive loss- es due to a high dcr. always consider the losses associated with the dcr and its effect on the total converter efficiency when selecting an inductor. the 4.7h cdrh3d16 series inductor selected from sumida has a 105m ? dcr and a 900ma dc current rating. at full load, the inductor dc loss is 17mw which gives a 2.8% loss in efficiency for a 400ma, 1.5v output. input capacitor select a 4.7f to 10f x7r or x5r ceramic capac- itor for the input. to estimate the required input capacitor size, determine the acceptable input rip- ple level (v pp ) and solve for c. the calculated value varies with input voltage and is a maximum when v in is double the output voltage. always examine the ceramic capacitor dc voltage coefficient characteristics when selecting the prop- er value. for example, the capacitance of a 10f, 6.3v, x5r ceramic capacitor with 5.0v dc applied is actually about 6f. the maximum input capacitor rms current is: the input capacitor rms ripple current varies with the input and output voltage and will always be less than or equal to half of the total dc load current. for v in = 2 x v obuck the term appears in both the input voltage ripple and input capacitor rms cur- rent equations and is a maximum when v obuck is twice v in . this is why the input voltage ripple and the input capacitor rms current ripple are a maxi- mum at 50% duty cycle. the input capacitor provides a low impedance loop for the edges of pulsed current drawn by the aat2500. low esr/esl x7r and x5r ceramic capacitors are ideal for this function. to minimize stray inductance, the capacitor should be placed as closely as possible to the ic. this keeps the high frequency content of the input current localized, minimizing emi and input voltage ripple. the proper placement of the input capacitor (c2) can be seen in the evaluation board layout in figure 3. a laboratory test set-up typically consists of two long wires running from the bench power supply to the evaluation board input voltage pins. the induc- tance of these wires, along with the low-esr ceramic input capacitor, can create a high q net- work that may affect converter performance. this problem often becomes apparent in the form of excessive ringing in the output voltage during load transients. errors in the loop phase and gain meas- urements can also result. since the inductance of a short pcb trace feeding the input voltage is significantly lower than the power leads from the bench power supply, most applications do not exhibit this problem. ?? 1 - ?? v obuck v in v obuck v in i obuck rms(max) i 2 = ?? 1 - = d (1 - d) = 0.5 2 = ?? v obuck v in v obuck v in 1 2 ?? i rms = i obuck 1 - ?? v obuck v in v obuck v in c in(min) = 1 ?? - esr 4 f s ?? v pp i obuck ?? 1 - = for v in = 2 v obuck ?? v obuck v in v obuck v in 1 4 ?? 1 - ?? v obuck v in c in = v obuck v in ?? - esr f s ?? v pp i obuck
in applications where the input power source lead inductance cannot be reduced to a level that does not affect the converter performance, a high esr tantalum or aluminum electrolytic should be placed in parallel with the low esr, esl bypass ceramic. this dampens the high q network and stabilizes the system. output capacitor the output capacitor limits the output ripple and provides holdup during large load transitions. a 22f x5r or x7r ceramic capacitor typically pro- vides sufficient bulk capacitance to stabilize the output during large load transitions and has the esr and esl characteristics necessary for low output ripple. the output voltage droop due to a load transient is dominated by the capacitance of the ceramic out- put capacitor. during a step increase in load cur- rent, the ceramic output capacitor alone supplies the load current until the loop responds. within two or three switching cycles, the loop responds and the inductor current increases to match the load current demand. the relationship of the output volt- age droop during the three switching cycles to the output capacitance can be estimated by: once the average inductor current increases to the dc load level, the output voltage recovers. the above equation establishes a limit on the minimum value for the output capacitor with respect to load transients. the internal voltage loop compensation also limits the minimum output capacitor value to 22f. this is due to its effect on the loop crossover frequency (bandwidth), phase margin, and gain margin. increased output capacitance will reduce the crossover frequency with greater phase margin. the maximum output capacitor rms ripple current is given by: dissipation due to the rms current in the ceramic output capacitor esr is typically minimal, resulting in less than a few degrees rise in hot-spot temperature. adjustable output resistor selection for applications requiring an adjustable output volt- age, the 0.6v version can be externally pro- grammed. resistors r1 and r2 of figure 5 program the output to regulate at a voltage higher than 0.6v. to limit the bias current required for the external feedback resistor string while maintaining good noise immunity, the minimum suggested value for 1 23 v out (v in(max) - v out ) rms(max) i l f v in(max) = c out = 3 ? i load v droop f s aat2506 1mhz step-down converter/ldo regulator 2506.2005.12.1.0 17 figure 3: aat2506 evaluation board top side. figure 4: aat2506 evaluation board bottom side.
aat2506 1mhz step-down converter/ldo regulator 18 2506.2005.12.1.0 r2 is 59k ? . although a larger value will further reduce quiescent current, it will also increase the impedance of the feedback node, making it more sensitive to external noise and interference. table 2 summarizes the resistor values for various output voltages with r2 set to either 59k ? for good noise immunity or 221k ? for reduced no load input current. the aat2506, combined with an external feedfor- ward capacitor (c8 in figures 2 and 5), delivers enhanced transient response for extreme pulsed load applications. the addition of the feedforward capacitor typically requires a larger output capaci- tor c1 for stability. table 2: adjustable resistor values for use with 0.6v step-down converter. r2 = 59k ? ? r2 = 221k ? ? v out (v) r1 (k ? ? ) r1 (k ? ? ) 0.8 19.6 75 0.9 29.4 113 1.0 39.2 150 1.1 49.9 187 1.2 59.0 221 1.3 68.1 261 1.4 78.7 301 1.5 88.7 332 1.8 118 442 1.85 124 464 2.0 137 523 2.5 187 715 3.3 267 1000 ?? ?? r1 = -1 r2 = - 1 59k ? = 88.5k ? v out v ref ?? ?? 1.5v 0.6v figure 5: aat2506 evaluation board schematic. 1. for step-down converter, enhanced transient configuration c8 = 100pf and c1 = 10uf. table 3 l1 22 f 1 c1 10 f c2 gnd v in1 1 2 3 buck enable lx1 gnd table 3 r1 59k r2 pgnd 1 lx 2 vp 3 vcc 4 enldo 9 en 10 fb 11 sgnd 12 in 5 out 6 gnd 8 byp 7 aat2506 u1 4.7 f c4 10 f c3 10nf c5 1 2 3 ldo enable v outldo v outbuck 1 2 3 ldo input 0.01 f c7 c8 1 n/a c9
thermal calculations there are three types of losses associated with the aat2506 step-down converter: switching losses, conduction losses, and quiescent current losses. conduction losses are associated with the r ds(on) characteristics of the power output switching devices. switching losses are dominated by the gate charge of the power output switching devices. at full load, assuming continuous conduction mode (ccm), a simplified form of the step-down convert- er and ldo losses is given by: i qbuck is the step-down converter quiescent cur- rent and i qldo is the ldo quiescent current. the term t sw is used to estimate the full load step-down converter switching losses. for the condition where the buck converter is in dropout at 100% duty cycle, the total device dissi- pation reduces to: since r ds(on) , quiescent current, and switching losses all vary with input voltage, the total losses should be investigated over the complete input voltage range. given the total losses, the maximum junction tem- perature can be derived from the ja for the tdfn33-12 package which is 50c/w. pcb layout the following guidelines should be used to ensure a proper layout. 1. the input capacitor c2 should connect as closely as possible to vp and pgnd, as shown in figure 4. 2. the output capacitor and inductor should be connected as closely as possible. the connec- tion of the inductor to the lx pin should also be as short as possible. 3. the feedback trace should be separate from any power trace and connect as closely as possible to the load point. sensing along a high-current load trace will degrade dc load regulation. if external feedback resistors are used, they should be placed as closely as pos- sible to the fb pin. this prevents noise from being coupled into the high impedance feed- back node. 4. the resistance of the trace from the load return to gnd should be kept to a minimum. this will help to minimize any error in dc regulation due to differences in the potential of the internal sig- nal ground and the power ground. 5. for good thermal coupling, pcb vias are required from the pad for the tdfn paddle to the ground plane. the via diameter should be 0.3mm to 0.33mm and positioned on a 1.2mm grid. 6. ldo bypass capacitor (c5) should be connected directly between pins 7 (byp) and 8 (gnd) t j(max) = p total ja + t amb p total = i obuck 2 r dson(hs) + i oldo (v in - v oldo ) + (i qbuck + i qldo ) v in p total i obuck 2 (r dson(hs) v obuck + r dson(ls) [v in - v obuck ]) v in = + (t sw f i obuck + i qbuck + i qldo ) v in + i oldo (v in - v oldo ) aat2506 1mhz step-down converter/ldo regulator 2506.2005.12.1.0 19
step-down converter design example specifications v obuck = 1.8v @ 400ma (adjustable using 0.6v version), pulsed load ? i load = 300ma v oldo = 3.3v @ 300ma v in = 2.7v to 4.2v (3.6v nominal) f s = 1.0mhz t amb = 85c 1.8v buck output inductor (see table 1) for sumida inductor cdrh3d16, 4.7h, dcr = 105m ? . 1.8v output capacitor v droop = 0.05v 1 23 1 1.8v (4.2v - 1.8v) 4.7 h 1.0mhz 4.2v 23 rms i l1 f v in(max) = 3 ? i load v droop f s 3 0.3a 0.05v 1mhz c out = = = 18 f = 63marms (v obuck ) (v in(max) - v obuck ) = p esr = esr i rms 2 = 5m ? (63ma) 2 = 20 w v obuck v obuck 1.8 v 1.8v ? i l1 = ? 1 - = ? 1 - = 218ma l1 ? f v in 4.7 h ? 1.0mhz 4.2v i pkl1 = i obuck + ? i l1 = 0.4a + 0.11a = 0.51a 2 p l1 = i obuck 2 ? dcr = 0.4a 2 ? 105m ? = 17mw ? ? ? ? ? ? ? ? 1 ? v o2 = 3 ? 1.8v = 5.4 h sec a sec a aat2506 1mhz step-down converter/ldo regulator 20 2506.2005.12.1.0
input capacitor input ripple v pp = 25mv aat2506 losses t j(max) = t amb + ja p loss = 85 c + (50 c/w) 392mw = 105 c p total + (t sw f i obuck + i qbuck + i qldo ) v in + (v in - v ldo ) i ldo i obuck 2 (r dson(hs) v obuck + r dson(ls) [v in - v obuck ] ) v in = = + (5ns 1.0mhz 0.4a + 50 a +125 a) 4.2v + (4.2v - 3.3v) 0.3a = 392mw 0.4 2 (0.725 ? 1.8v + 0.7 ? [4.2v - 1.8v]) 4.2v i obuck rms i p = esr i rms 2 = 5m ? (0.2a) 2 = 0.2mw 2 = = 0.2arms c in = = = 4.75 f 1 ?? - esr 4 f s ?? v pp i obuck 1 ?? - 5m ? 4 1mhz ?? 25mv 0.4a aat2506 1mhz step-down converter/ldo regulator 2506.2005.12.1.0 21
table 3: evaluation board component values. table 4: typical surface mount inductors. inductance max dc dcr size (mm) manufacturer part number (h) current (a) ( ? ? ) lxwxh type sumida cdrh3d16-4r7 4.7 0.90 0.11 4.0x4.0x1.8 shielded sumida cdrh3d16-100 10 0.55 0.21 4.0x4.0x1.8 shielded murata lqh32cn4r7m23 4.7 0.45 0.20 2.5x3.2x2.0 non-shielded murata lqh32cn4r7m33 4.7 0.65 0.15 2.5x3.2x2.0 non-shielded murata lqh32cn4r7m53 4.7 0.65 0.15 2.5x3.2x1.55 non-shielded coilcraft lpo6610-472 4.7 1.10 0.20 5.5x6.6x1.0 1mm coilcraft LPO3310-472 4.7 0.80 0.27 3.3x3.3x1.0 1mm coiltronics sdrc10-4r7 4.7 1.53 0.117 4.5x3.6x1.0 1mm shielded coiltronics sdr10-4r7 4.7 1.30 0.122 5.7x4.4x1.0 1mm shielded coiltronics sd3118-4r7 4.7 0.98 0.122 3.1x3.1x1.85 shielded coiltronics sd18-4r7 4.7 1.77 0.082 5.2x5.2x1.8 shielded v out (v) r1 (k ? ? ) r1 (k ? ? ) l1 (h) adjustable version r2 = 59k ? ? r2 = 221k ? ? 1 1 (0.6v device) 0.8 19.6 75.0 4.7 0.9 29.4 113 4.7 1.0 39.2 150 4.7 1.1 49.9 187 4.7 1.2 59.0 221 4.7 1.3 68.1 261 4.7 1.4 78.7 301 4.7 1.5 88.7 332 4.7 1.8 118 442 4.7 1.85 124 464 4.7 2.0 137 523 4.7 or 6.8 2.5 187 715 10 3.3 267 1000 10 v out (v) r1 (k ? ? ) l1 (h) fixed version r2 not used 0.6-3.3v 0 4.7 aat2506 1mhz step-down converter/ldo regulator 22 2506.2005.12.1.0 1. for reduced quiescent current r2 = 221k ? .
table 5: surface mount capacitors. manufacturer part number value voltage temp. co. case murata grm21br60j226me39 22f 6.3v x5r 0805 tdk c2012x5r0j226k 22f 6.3v x5r 0805 taiyo-yuden jmk212bj226kl 22f 6.3v x5r 0805 aat2506 1mhz step-down converter/ldo regulator 2506.2005.12.1.0 23
ordering information all analogictech products are offered in pb-free packaging. the term ?pb-free? means semiconductor products that are in compliance with current rohs standards, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. for more information, please visit our website at http://www.analogictech.com/pbfree. voltage package buck converter ldo marking 1 part number (tape and reel) 2 tdfn33-12 adj - 0.6v 3.3v tdfn33-12 adj - 0.6v 3.0v tdfn33-12 adj - 0.6v 2.8v qqxyy aat2506iwp-aq-t1 tdfn33-12 adj - 0.6v 2.7v tdfn33-12 adj - 0.6v 2.5v tdfn33-12 adj - 0.6v 1.8v tdfn33-12 adj - 0.6v 1.5v tdfn33-12 1.2v 3.0v tdfn33-12 1.8v 2.7v aat2506 1mhz step-down converter/ldo regulator 24 2506.2005.12.1.0 legend voltage code adjustable a (0.6v) 1.2 e 1.5 g 1.8 i 1.9 y 2.5 n 2.6 o 2.7 p 2.8 q 2.85 r 2.9 s 3.0 t 3.3 w 1. xyy = assembly and date code. 2. sample stock is generally held on part numbers listed in bold .
package information tdfn33-12 top view bottom view detail "b" detail "a" side view 3.00 0.05 index area (d/2 x e/2) detail "a" detail "b" 1.70 0.05 3.00 0.05 0.05 0.05 0.229 0.051 7.5 7.5 2.40 0.05 0.16 pin 1 indicator (optional) 0.375 0.125 0.3 0.10 0.45 0.05 0.23 0.05 0.075 0.075 0.1 ref 0.8 + 0.05 -0.20 option a: c0.30 (4x) max chamfered corner option b: r0.30 (4x) max round corner aat2506 1mhz step-down converter/ldo regulator 2506.2005.12.1.0 25
aat2506 1mhz step-down converter/ldo regulator 26 2506.2005.12.1.0 advanced analogic technologies, inc. 830 e. arques avenue, sunnyvale, ca 94085 phone (408) 737-4600 fax (408) 737-4611 ? advanced analogic technologies, inc. analogictech cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in an analogictech pr oduct. no circuit patent licenses, copyrights, mask work rights, or other intellectual property rights are implied. analogictech reserves the right to make changes to their products or specifi cations or to discontinue any product or service without notice. customers are advised to obtain the latest version of relevant information to verify, before placing orders, that information b eing relied on is current and complete. all products are sold subject to the terms and conditions of sale supplied at the time of order acknowledgement, including those pertaining to warran ty, patent infringement, and limitation of liability. analogictech warrants performance of its semiconductor products to the specifications applicable at the time of sale in accordance with anal ogictech?s standard warranty. testing and other quality con- trol techniques are utilized to the extent analogictech deems necessary to support this warranty. specific testing of all param eters of each device is not necessarily performed.

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